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AD8361 Datasheet(Fiches technique) 14 Page - Analog Devices

Numéro de pièce AD8361
Description  LF to 2.5 GHz TruPwr™ Detector
Télécharger  16 Pages
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Fabricant  AD [Analog Devices]
Site Internet  http://www.analog.com
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AD8361
–14–
REV. A
chosen to suit the application. GAIN and VOS are then calculated
using the equations:
GAIN
VV
VV
OUT
OUT
IN
IN
=
()
()
21
21
V
V
GAIN
V
OS
OUT
IN
=−
×
()
11
Both GAIN and VOS drift over temperature. However, the drift
of VOS has a bigger influence on the error relative to the output.
This can be seen by inserting data from Figures 14 and 17 (con-
version gain and intercept drift) into the equation for VOUT. These
plots are consistent with Figures 10 and 11 which show that the
error due to temperature drift decreases with increasing input
level. This results from the offset error having a diminishing
influence with increasing level on the overall measurement error.
From Figure 14, the average Intercept drift is 0.43 mV/
°C from
–40
°C to +25°C and 0.17 mV/°C from +25°C to +85°C. For a
less rigorous compensation scheme, the average drift over the
complete temperature range can be calculated:
DRIFT
V
C
VV
CC
VOS
/
..
°
() =
−−
()
+° − − °
()
0 010
0 028
85
40
= 0.000304 V/
°C
With the drift of VOS included, the equation for VOUT becomes:
Table V. Evaluation Board Configuration Options
Component
Function
Default Condition
TP1, TP2
Ground and Supply Vector Pins.
Not Applicable
SW1
Device Enable. When in Position A, the PWDN pin is connected to +VS and
SW1 = B
the AD8361 is in power-down mode. In Position B, the PWDN pin is grounded,
putting the device in operating mode.
SW2/SW3
Operating Mode. Selects either Ground Referenced Mode, Internal Reference
SW2 = A, SW3 = B
Mode or Supply Reference Mode. See Table I for more details.
(Ground Reference Mode)
C1, R2
Input Coupling. The 75
Ω resistor in position R2 combines with the AD8361’s
R2 = 75
Ω (Size 0402)
internal input impedance to give a broadband input impedance of around 50
Ω.
C1 = 100 pF (Size 0402)
For more precise matching at a particular frequency, R2 can be replaced by a
different value (see Input Matching and Figure 39).
Capacitor C1 ac-couples the input signal and creates a high-pass input filter
whose corner frequency is equal to approximately 8 MHz. C1 can be increased
for operation at lower frequencies. If resistive attenuation is desired at the input,
series resistor R1, which is nominally 0
Ω, can be replaced by an appropriate value.
C2, C3, R6
Power Supply Decoupling. The nominal supply decoupling of 0.01
µF and
C2 = 0.01
µF (Size 0402)
100 pF. A series inductor or small resistor can be placed in R6 for additional
C3 = 100 pF (Size 0402)
decoupling.
R6 = 0
Ω (Size 0402)
C5
Filter Capacitor. The internal 50 pF averaging capacitor can be augmented
C5 = 1 nF (Size 0603)
by placing a capacitance in C5.
C4, R5
Output Loading. Resistors and capacitors can be placed in C4 and R5 to
C4 = R5 = Open
load test V rms.
(Size 0603)
V
GAIN
V
V
DRIFT
TEMP
C
OUT
IN
OS
VOS
()++
×
− °
()
25
The equation can be rewritten to yield a temperature compen-
sated value for VIN.
V
V
V
DRIFT
TEMP
C
GAIN
IN
OUT
OS
VOS
=
−−
×
− °
()
()
25
EVALUATION BOARD
Figures 43 and 46 show the schematic of the AD8361 evalua-
tion board. Note that uninstalled components are drawn in as
dashed. The layout and silkscreen of the component side are
shown in Figures 44, 45, 47, and 48. The board is powered by a
single supply in the range, 2.7 V to 5.5 V. The power supply
is decoupled by 100 pF and 0.01
µF capacitors. Additional
decoupling, in the form of a series resistor or inductor in R6,
can also be added. Table V details the various configuration
options of the evaluation board.




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